Oscillating apparatus

ABSTRACT

An oscillating apparatus is provided that includes: an integration circuit that outputs a control signal based on an integration value of two inputted voltage values; an oscillator that outputs an oscillation signal of a frequency that is based on the control signal; a phase comparator that outputs a phase difference signal of a pulse width that is in accordance with a phase difference between the oscillation signal and the reference signal, by comparing the oscillation signal with a reference signal of a predetermined frequency; a controlling circuits that controls the two inputted voltage values based on the phase difference signal, so as to approximate a phase difference between the oscillation signal and the reference signal to a predetermined reference phase difference; and a voltage stabilizing current that defines the two inputted voltages based on a predetermined reference voltage.

CROSS REFERENCE TO RELATED APPLICATION

This is a divisional application of an application Ser. No. 11/776,550,filed on Jul. 11, 2007, now pending, which is a continuation applicationof PCT/JP2006/305591 filed on Mar. 20, 2006 which claims priority from aJapanese Patent Application(s) No. 2005-084575 filed on Mar. 23, 2005,the contents of which are incorporated herein by reference.

BACKGROUND

1. Technical Field

The present invention relates to an oscillating apparatus for generatinga signal based on a reference signal. In particular, the presentinvention relates to an oscillating apparatus for generating a signalwith use of a PLL circuit.

2. Description of the Related Art

Normally, PLL (Phase Lock Loop) circuits have been widely used ascircuits generating a signal with high accuracy. A PLL circuit comparesthe frequency of a reference signal and the frequency of an oscillationsignal by means of a phase comparator, and changes the frequency of theoscillation signal based on the detected phase difference. It is known,however, that the phase comparator cannot detect a minute phasedifference in some cases. The range of such undetected phase differenceis referred to as a dead zone.

There has been known a method of using a timing shift current (It) inaddition to a charge pump current (Ic) in the PLL circuit, as one methodof compensating the existence of such a dead zone. FIG. 11 shows a PLLcircuit 60 of a conventional charge pump type. The PLL circuit 60includes a filter circuit 600, an oscillator 610, a frequency divider615, a phase comparator 620, a reference signal generator 625, a switchcircuit 630, a charge current supply 640, and a charge pump currentsupply 650.

The filter circuit 600 includes a capacitor 605, and outputs a controlsignal that is based on the amount of charge accumulated in thecapacitor 605. The oscillator 610 outputs an oscillation signal of afrequency that is based on the control signal. The frequency divider 615either divides or multiplies the frequency of the oscillation signal,and outputs the result to the phase comparator 620. The phase comparator620 compares the oscillation signal with the reference signal outputtedfrom the reference signal generator 625, and detects the phasedifference between the oscillation signal and the reference signal. Theswitch circuit 630, based on the phase difference, controls whether tocharge the capacitor 605 according to a timing shift current (It)outputted from the charge current supply 640, or to discharge thecapacitor 605 according to a predetermined discharge current (I−It).

Currently, we have not recognized any existence of prior art reference,and so the description thereof is omitted.

FIG. 12 shows an effect that the charge current and the charge pumpcurrent give to the phase difference in the PLL circuit 60. Thereference signal generator 625 generates a reference signal having aperiod T. In a certain stationary state, the oscillator 610 isoutputting an oscillation signal whose phase difference from thereference signal is t. In such a state, when the oscillation signal hasa phase difference with respect to the reference signal, the phasecomparator 620 outputs a pulse (signal A) corresponding to the phasedifference at the time of rising-up of the signal. Otherwise, the phasecomparator 620 outputs a signal B. As a result, charge is accumulated inthe capacitor 605 when the signal A is outputted, and charge isdischarged from the capacitor 605 when the signal B is outputted.

Here, the oscillation signal is in a stationary state, and that itsfrequency is not changed. Therefore it means that the amount of chargeaccumulated in the capacitor 605 is undergoing a transition in thevicinity of a certain standard (X). Accordingly, the amount of chargeaccumulated by output of the signal A is equal to the amount of chargedischarged by output of the signal B. Consequently, the followingequation (1) is derived.t(Ic−It)=(T−t)It  equation (1)

By modifying this equation, the following equation (2) is derived.tIc=TItt=T×It/Ic  equation (2)

Consequently, the phase difference t is determined based on the ratiobetween the current values of It and Ic.

There are cases where the sizes of these current values fluctuateaccording to the fluctuation of the temperature both inside and outsidethe apparatus, or the fluctuation of the power supply voltage.Conventionally, there have been cases where, when the fluctuation ratiosof It and Ic are different from each other, the phase difference t alsofluctuates due to the fluctuation.

Additionally, as one index of representing the characteristics of a PLLcircuit, a loop band is known which is a frequency band of a jittercomponent followable by the circuit. This loop band is defined by thecharacteristics of a PLL circuit, e.g. characteristics of the oscillator610, the size of the charge pump current, etc. Depending on theapplication of the PLL circuit, this loop band is desired to bevariable. For example, suppose a case where, in the oscillator 610, thecharacteristics representing the frequency of the oscillation signal pervoltage value of an applied voltage fluctuates according to the size ofthe frequency. In such a case and the like, if the loop band can bevaried, it becomes possible to prevent the loop band of the PLL fromfluctuating attributable to the output frequency.

For changing the loop band of a PLL circuit, there are two possiblemethods as follows. The first method is to change the gain of the filtercircuit by a switch. The second method is to switch the charge pumpcurrent value by a switch. According to these methods, however, switchescorresponding in number to the minuteness of the variable resolution ofthe loop band become necessary. In view of this, a multitude of switchesbecome necessary, which would lead to increase in complication of thecircuit or increase in power consumption. A method of adjusting thecurrent value of the charge pump current by means of a DA converter canbe also considered. However in such a case, the above-mentioned phasedifference t may fluctuate by change in the characteristics of the DAconverter in response to the effect from the temperature change, and thelike.

SUMMARY

In view of this, as one aspect, it is an advantage of the presentinvention to provide an oscillating apparatus for generating a signalbased on a reference signal, which is able to solve the above-mentionedproblems. This advantage is achieved by combinations of the featuresdescribed in the independent claims. The dependent claims further defineadvantageous concrete examples of the present invention.

According to the first aspect related to the innovations herein, oneexemplary oscillating apparatus may include: a filter circuit thatincludes a capacitor and outputs a control signal based on an amount ofcharge accumulated in the capacitor; an oscillator that outputs anoscillation signal of a frequency that is based on the control signal; aphase comparator that compares the oscillation signal with a referencesignal of a predetermined frequency, to detect a phase differencebetween the oscillation signal and the reference signal; a switchcircuit that controls whether to charge the capacitor according to apredetermined charge current or to discharge the capacitor according toa predetermined discharge current, based on the phase difference; and acurrent stabilizing current that defines each of the charge current andthe discharge current based on a predetermined reference current or areference voltage.

According to the second aspect related to the innovations herein, oneexemplary oscillating apparatus may include: an integration circuit thatoutputs a control signal based on an integration value of two inputtedvoltage values; an oscillator that outputs an oscillation signal of afrequency that is based on the control signal; a phase comparator thatoutputs a phase difference signal of a pulse width that is in accordancewith a phase difference between the oscillation signal and the referencesignal, by comparing the oscillation signal with a reference signal of apredetermined frequency; a controlling circuit that controls the twoinputted voltage values based on the phase difference signal, so as toapproximate a phase difference between the oscillation signal and thereference signal to a predetermined reference phase difference; and avoltage stabilizing circuit that defines the two inputted voltage valuesboth based on a predetermined reference voltage.

The summary clause does not necessarily describe all necessary featuresof the embodiments of the present invention. The present invention mayalso be a sub-combination of the features described above.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows a configuration of an oscillating apparatus 10 according toa first embodiment of the present invention.

FIG. 2 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (First Example).

FIG. 3 shows a modification example of the charge pump current supply150 shown in FIG. 2.

FIG. 4 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Second Example).

FIG. 5 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Third Example).

FIG. 6 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Fourth Example).

FIG. 7 shows a configuration of an oscillating apparatus 10 according toa second embodiment of the present invention.

FIG. 8 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 7.

FIG. 9 shows a configuration of an oscillating apparatus 10 according toa third embodiment of the present invention.

FIG. 10 shows a waveform of each control signal, in the oscillatingapparatus 10 shown in FIG. 9.

FIG. 11 shows a PLL circuit 60 of a conventional charge pump type.

FIG. 12 shows an effect that the charge current and the charge pumpcurrent give to the phase difference in the PLL circuit 60.

DESCRIPTION OF EXEMPLARY EMBODIMENTS

Some aspects of the invention will now be described based on theembodiments, which do not intend to limit the scope of the presentinvention, but exemplify the invention. All of the features and thecombinations thereof described in the embodiment are not necessarilyessential to the invention.

FIG. 1 shows a configuration of an oscillating apparatus 10 according toa first embodiment of the present invention. The oscillating apparatus10 includes a filter circuit 100, an oscillator 110, a frequency divider115, a phase comparator 120, a reference signal generator 125, a switchcircuit 130, a current stabilizing circuit 140, and a reference currentsupply 155. The filter circuit 100 includes a capacitor 105 and a filter108, and outputs a control signal that is based on the amount of chargeaccumulated in the capacitor 105 to the oscillator 110 via the filter108. The oscillator 110 outputs an oscillation signal of a frequencythat is based on the control signal to outside. To be more specific, thefrequency of an oscillation signal is defined based on a voltage valueof a control signal outputted from the filter circuit 100.

The frequency divider 115 divides or multiplies the frequency of anoscillation signal outputted from the oscillator 110 at a predeterminedratio, and outputs the result to the phase comparator 120. The referencesignal generator 125 outputs a reference signal of a predeterminedfrequency to the phase comparator 120. The phase comparator 120 comparesthe oscillation signal inputted from the oscillator 110 via thefrequency divider 115 and the reference signal inputted from the phasecomparator 120, to detect the phase difference between the oscillationsignal and the reference signal.

Based on the phase difference detected by the phase comparator 120, theswitch circuit 130 controls whether to charge the capacitor 105according to a predetermined charge current (It) or to discharge thecapacitor 105 according to a predetermined discharge current (Ic−It).The current stabilizing circuit 140 defines the charge current and thecharge pump current respectively based on a predetermined referencecurrent (Iref). In this way, the charge current and the charge pumpcurrent are respectively defined based on the current value of thereference current supply 155. According to this arrangement, the chargecurrent (It) and the discharge current (Ic−It) are prevented from beingsubjected to different effects from each other even when the temperatureor the power supply voltage has fluctuated, thereby stabilizing thephase difference regarding the oscillation signal, and reducing thejitter.

FIG. 2 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (First Example). The current stabilizing circuit 140includes a charge pump current supply 150, a phase controlling currentsupply 160, and a current adjusting circuit 170. The charge pump currentsupply 150 runs a predetermined charge pump current (Ic) of a sizecorresponding to a summation of the charge current (It) and thedischarge current (Ic−It). The charge pump current supply 150, whenbeing connected to the capacitor 105 via the switch circuit 130,discharges the capacitor 105 according to the discharge current (Ic−It).To be more specific, the charge pump current supply 150 has a currentmirror circuit 158 connected to the first reference potential (V−), andruns the charge pump current (Ic) and the phase controlling current (Ia)substantially proportional to the reference current (Iref), to the firstreference potential (V−) by means of the current mirror circuit 158.

The phase controlling current supply 160 is connected to the capacitor105, and runs the phase controlling current (It) to the capacitor 105.When the switch circuit 130 has cut off the connection between thecapacitor 105 and the current stabilizing circuit 140, the capacitor 105is charged according to the phase controlling current (It). To be morespecific, the phase controlling current supply 160 has a current mirrorcircuit 165 connected to the second reference potential (V+) that ishigher than the first reference potential (V−), and the current mirrorcircuit 165 runs the phase controlling current (It) that issubstantially proportional to the consultation current (K×Ia), from thesecond reference potential (V+) to the capacitor 105. It should be notedthat the current mirror circuit 165 becomes unnecessary when thelater-detailed phase controlling current changing circuit 172 isrealized by means of a DA converter of a current release type. That is,in that case, the phase controlling current supply 160 may directlysupply the current outputted from the phase controlling current changingcircuit 172 to the capacitor 105.

The current adjusting circuit 170 includes a phase controlling currentchanging circuit 172 and a charge pump current changing circuit 175. Thephase controlling current changing circuit 172 is for example realizedby a DA converter and the like, and changes the size of the phasecontrolling current by setting the ratio of the consultation currentgiven to the phase controlling current supply 160 with respect to thereference current (Iref) to a designated value. The size of theconsultation current resulting from the changing is assumed to be K×Ia.The charge pump current changing circuit 175 is for example realized bya DA converter and the like, and sets the ratio of the charge pumpcurrent (Ic) with respect to the reference current (Iref) to adesignated value. According to the setting of this ratio, it is possibleto set the response characteristic being the change amount of thefrequency of the oscillation signal with respect to the fluctuationamount of the phase difference between the reference signal and theoscillation signal. Furthermore, by changing this responsecharacteristic, it becomes possible to arbitrarily define the loop bandas a PLL circuit.

To be specific, the charge pump current changing circuit 175 isconnected to the switch circuit 130 via the current mirror circuit 190and the current mirror circuit 195 sequentially. The current mirrorcircuit 190 is connected to the positive voltage (Vcc) of the circuitpower supply, and runs the current substantially proportional to theintake current of the charge pump current changing circuit 175, to thecurrent mirror circuit 195. The current mirror circuit 195 is connectedto the negative voltage (Vee) of the current power supply, and runs thecharge pump current (Ic) substantially proportional to the current runby the current mirror circuit 190, from the switch circuit 130.Accordingly, it becomes possible to run the current of a predeterminedsize as the charge pump current, regardless of the characteristics ofthe DA converter realizing the charge pump current changing circuit 175.It should be noted that, depending on the characteristics of the DAconverter, the charge pump current changing circuit 175 may be directlyconnected to the switch circuit 130.

Furthermore, in changing the ratio of the charge pump current (Ic) withrespect to the reference current (Iref), it is preferable that thecurrent adjusting circuit 170 changes the phase controlling current (It)too, so as to maintain the ratio between the charge pump current (Ic)and the phase controlling current (It) as it is before the change.According to this, it becomes possible to change only the responsecharacteristic, by maintaining the phase difference of the oscillationsignal with respect to the reference signal constant.

Moreover, it is further preferable that, when the time elapsed after theoscillating apparatus 10 has started outputting an oscillation signal isshorter, the current adjusting circuit 170 sets the response speed forchanging the frequency in response to the fluctuation of the phasedifference, to be faster than when the elapsed time is longer. Accordingto this, when the phase difference between the oscillation signal andthe reference signal is large at the time of power supply throwing andthe like, it is possible to match the frequency to the reference signalswiftly as well as making it harder to be subjected to the effect of aminute fluctuation of the frequency of the reference signal when thefrequency has been stabilized thereafter.

FIG. 3 shows a modification example of the charge pump current supply150 shown in FIG. 2. In this modification example, the charge pumpcurrent supply 150 includes a reference voltage supply 300, a chargepump current generating circuit 310, and a phase controlling currentgenerating circuit 320. The reference voltage supply 300 is connected tothe first reference potential (V−), and defines the potential of whichthe potential difference from the first reference potential is set asthe reference voltage value (Vref). The charge pump current generatingcircuit 310 runs the current (I₁) that is proportional to the size ofthe reference voltage value (Vref), to the first reference potential.The current (I₁) corresponds to a value obtained by dividing thereference voltage value (Vref) by a reference resistance value (R1). Inaddition, the phase controlling current generating circuit 320 runs thephase controlling current (I₂) proportional to the size of the referencevoltage value (Vref), to the first reference potential. The phasecontrolling current (I₂) corresponds to a value obtained by dividing thereference voltage value (Vref) by a reference resistance value (R2).

In this way, a common reference for determining the charge current andthe discharge current may also be the reference voltage not only thereference current. According to such a configuration too, it becomespossible to equalize the effect undergone by the charge current and thedischarge current such as a temperature fluctuation and the like.Therefore, it becomes possible to maintain the phase difference of theoscillation signal with respect to the reference signal constant.

FIG. 4 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Second Example). As in the same way as in FIG. 2,the current stabilizing circuit 140 includes a charge pump currentsupply 150, a phase controlling current supply 160, and a currentadjusting circuit 170. In the example of this diagram, however, thecharge pump current supply 150 is connected to the first referencepotential (V−), unlike in FIG. 2. The charge pump current supply 150runs a charge pump current substantially proportional to a predeterminedconsultation current, from the switch circuit 130 to the first referencepotential. For running the substantially proportional current, it ispossible to use a current mirror circuit 158, for example.

The phase controlling current supply 160 is connected to the secondreference potential that is higher than the first reference potential(V−), unlike in the example of FIG. 2. The phase controlling currentsupply 160 runs a consultation current and a phase controlling currentsubstantially proportional to a reference current, from the secondreference potential (V+) to the charge pump current supply 150 and thecapacitor 105. For running the substantially proportional current, it ispossible to use a current mirror circuit 165, for example.

The current adjusting circuit 170 includes a phase controlling currentchanging circuit 172 and a charge pump current changing circuit 175, asin the same way as in FIG. 2. The phase controlling current changingcircuit 172 is for example realized by a DA converter and the like, andsets the ratio of the phase controlling current with respect to thereference current (Iref), to a designated value. The charge pump currentchanging circuit 175 is for example realized by a DA converter and thelike, and changes the ratio of the charge pump current (Ic) with respectto the reference current (Iref), to a designated value. According to thesetting of this ratio, it is possible to set the response characteristicbeing the change amount of the frequency of the oscillation signal withrespect to the fluctuation amount of the phase difference between thereference signal and the oscillation signal. Furthermore, by changingthis response characteristic, it becomes possible to arbitrarily definethe loop band as a PLL circuit.

FIG. 5 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Third Example). In this example, as in the same wayas the current adjusting circuit 170 shown in FIG. 2, the charge pumpcurrent supply 150 includes a phase controlling current changing circuit172 and a charge pump current changing circuit 175. However, differentfrom FIG. 2, both of the phase controlling current changing circuit 172and the charge pump current changing circuit 175 input a predeterminedreference voltage. The phase controlling current changing circuit 172sets the ratio of the phase controlling current with respect to thereference voltage to a designated value, and outputs the ratio to thephase controlling current supply 160. The charge pump current changingcircuit 175 changes the response characteristic of the oscillationsignal by setting the ratio of the charge pump current with respect tothe reference voltage to a designated value. The other configurationsare substantially the same as those of the current stabilizing circuit140 shown in FIG. 2, and so the description thereof is omitted in thefollowing.

As in the above, according to the present example too, it is possible todefine the current values of the charge pump current and of the chargecurrent based on a common reference voltage. Accordingly, it becomespossible to equalize the effect undergone by the charge current and thedischarge current such as a temperature fluctuation and the like.Therefore, it becomes possible to maintain the phase difference of theoscillation signal with respect to the reference signal constant.

FIG. 6 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 1 (Fourth Example). In the present example, as theconfiguration shown in FIG. 2, the current stabilizing circuit 140includes a charge pump current supply 150, a phase controlling currentsupply 160, and a current adjusting circuit 170. Note here thatdifferent from FIG. 2, the current adjusting circuit 170 includes areference current changing circuit 180 instead of a charge pump currentchanging circuit 175. The reference current changing circuit 180 is forexample realized by a DA converter and the like, and sets the currentvalue of the reference current to a designated value. The charge pumpcurrent supply 150 runs a charge pump current substantially proportionalto the reference current, and runs a phase controlling currentsubstantially proportional to the reference current.

As a result, by changing the current value of a reference current, itbecomes possible to change only the response characteristic being thechange amount of the frequency of the oscillation signal with respect tothe fluctuation amount of the phase difference, while maintaining theratio between the charge pump current and the charge current constant.In addition, just as in the same way as in FIG. 2, it is possible tochange the ratio between the charge pump current and the charge currentby means of the phase controlling current changing circuit 172.Therefore, it is also possible to arbitrarily set the phase differenceof the oscillation signal with respect to the reference signal.

FIG. 7 shows a configuration of an oscillating apparatus 10 according toa second embodiment of the present invention. As in the same way as inFIG. 1, the oscillating apparatus 10 includes a filter circuit 100, anoscillator 110, a frequency divider 115, a phase comparator 120, areference signal generator 125, a switch circuit 130, a currentstabilizing circuit 140, and a reference current supply 155. As follows,the differences from FIG. 1 are described. The switch circuit 130controls whether to discharge the capacitor 105 according to apredetermined discharge current (It) or to charge the capacitor 105according to a predetermined charge current (Ic−It), based on the phasedifference detected by the phase comparator 120. The current stabilizingcircuit 140 defines the charge pump current (Ic) and the phasecontrolling current (It) both based on the reference current (Iref).Consequently, each of the charge current and the discharge current isdefined based on the reference current (Iref). According to thisarrangement, the charge current and the discharge current are preventedfrom being subjected to different effects from each other even when thetemperature or the power supply voltage has fluctuated, therebystabilizing the phase difference regarding the oscillation signal, andreducing the jitter.

FIG. 8 shows a detailed configuration of the current stabilizing circuit140 shown in FIG. 7. As in the same way as in FIG. 2, the currentstabilizing circuit 140 includes a charge pump current supply 150, aphase controlling current supply 160, and a current adjusting circuit170. As follows, the differences from FIG. 2 are described. The chargepump current supply 150 runs a predetermined charge pump (Ic), and whenbeing connected to the capacitor 105 via the switch circuit 130, thecharge pump current supply 150 charges the capacitor 105. Concretely,the charge pump current supply 150 has a current mirror circuit 158connected to the second reference potential (V+), and runs the chargepump current (Ic) that is substantially proportional to the consultationcurrent, to the switch circuit 130 by means of the current mirrorcircuit 158.

The phase controlling current supply 160 is connected to the capacitor105, and sets a predetermined phase controlling current as a dischargecurrent, and discharges the capacitor 105 according to the dischargecurrent. Concretely, the phase controlling current supply 160 has acurrent mirror circuit 165 connected to the first reference potential(V−) that is lower than the second reference potential (V+), and thecurrent mirror circuit 165 runs a consultation current (Ia) and a phasecontrolling current (It) substantially proportional to the referencecurrent (Iref).

The current adjusting circuit 170 includes a phase controlling currentchanging circuit 172 and a charge pump current changing circuit 175. Thephase controlling current changing circuit 172 is for example realizedby a DA converter and the like, and changes the size of the phasecontrolling current by setting the ratio of the phase controllingcurrent with respect to the reference current (Iref) to a designatedvalue. The charge pump current changing circuit 175 is for examplerealized by a DA converter and the like, and sets the ratio of thecharge pump current (Ic) with respect to the consultation current (Ia)to a designated value. According to the setting of this ratio, it ispossible to set the response characteristic being the change amount ofthe frequency of the oscillation signal with respect to the fluctuationamount of the phase difference between the reference signal and theoscillation signal.

FIG. 9 shows a configuration of an oscillating apparatus 10 according toa third embodiment of the present invention. FIG. 10 shows a waveform ofeach control signal, in the oscillating apparatus 10 shown in FIG. 9.The oscillating apparatus 10 includes an integration circuit 900, anoscillator 910, a frequency divider 915, a phase comparator 920, areference signal generator 925, a controlling circuit 930, and a voltagestabilizing circuit 940. The oscillator 910, the frequency divider 915,and the reference signal generator 925 are substantially the same as theoscillator 110, the frequency divider 115, and the reference signalgenerator 125 explained with reference to FIG. 1, and so the descriptionthereof is omitted in the following. The integration circuit 900 outputsa control signal based on an integration value of two inputted voltagevalues. As one example, the integration circuit 900 is realized by acircuit that feeds back an output of the comparator to the input side.

The phase comparator 920 compares an oscillation signal with a referencesignal of a predetermined frequency. The phase comparator 920 outputs aphase difference signal having a pulse width that is in accordance withthe phase difference between the oscillation signal and the referencesignal. For example, when the phase of the oscillation signal is delayedwith respect to the reference signal, the phase comparator 920 outputs asignal having a pulse width that is in accordance with the delay, to aterminal U at the time of rising-up of the reference signal (See V_(U)in FIG. 10). In this case, the phase comparator 902 does not output asignal to the terminal D. However, depending on the specification of thecircuit device realizing the phase comparator 920, there are cases wherean extremely small pulse occurs at the time of rising-up of thereference signal.

The controlling circuit 930 controls the two inputted voltage valuesbased on a phase difference signal, so as to approximate the phasedifference between the oscillation signal and the reference signal to apredetermined reference phase difference. To be more specific, thecontrolling circuit 930 generates a voltage (V_(U)) and a voltage(V_(D)), based on voltage values respectively of the terminal U and theterminal D of the phase comparator 920. Furthermore, the controllingcircuit 930 generates a predetermined phase controlling voltage (Vc).Then the controlling circuit 930 sets the phase controlling voltage (Vc)and the voltage (V_(D)) as one inputted voltage value with respect tothe integration circuit 900, and the voltage (V_(U)) as the otherinputted voltage value. The voltage stabilizing circuit 940 defines thetwo inputted voltage values both based on a predetermined referencevoltage (Vref).

Here, when the frequency of the oscillation signal makes a stabletransition, current values of the two currents inputted to theintegration circuit 900 are equalized, since the voltage of a controlsignal inputted to the oscillator 910 is stabilized. That is, therelationship among the current (Ic) generated by the phase controllingvoltage (Vc), the current (I_(U)) generated by the voltage (V_(U)), andthe current (I_(D)) generated by the voltage (V_(D)) is Ic+I_(D)=I_(U).In this case, V_(U)=Vc+V_(D). Now suppose that the voltage (Vc) isexpressed as Vc=Vl+(Vh−Vl), by using one level voltage (Vh) and theother level voltage (Vl) of the voltage (V_(U)).

In this case, the controlling circuit 930 controls so that the voltagevalue inputted to the integration circuit 900 is equalized, by delayingthe oscillation signal with respect to the reference signal by ¼ period.In this way, according to the present embodiment, by appropriatelydefining the size of the phase controlling voltage, it becomes possibleto define the reference potential difference of the oscillation signalwith respect to the reference signal. Moreover, the phase comparator 920and the controlling circuit 930 are able to control the phase differenceof the oscillation signal with respect to the reference signal, to beapproximated to this reference potential difference.

In addition, the loop band in the present embodiment is defined based oneach element of the sensitivity of the oscillator 910, the gain of theloop filter, and the amplitude of the inputted voltage value to theintegration circuit 900. For example, the reference voltage (Vref) shownin FIG. 9 may be changed so as to change the amplitude of the inputtedvoltage value. In this way, according to the present embodiment, too, itis possible to arbitrarily define the loop band, just as in the otherembodiments described above.

It should be noted that the circuitry configuration shown in FIG. 9 isonly an example, and various types of modification examples areconsidered. For example, the phase controlling voltage (Vc) may beapplied to any input terminal of the integration circuit 900. Inaddition, the integration circuit 900 may set a predetermined constantvoltage value defined based on the reference voltage (Vref) as an input,instead of the inputted voltage value (V_(U)). In this case, too, thephase comparator 920 and the controlling circuit 930 are able to definethe phase difference of the oscillation signal with respect to thereference signal, to a predetermined phase difference.

Although some aspects of the present invention have been described byway of exemplary embodiments, it should be understood that those skilledin the art might make many changes and substitutions without departingfrom the spirit and the scope of the present invention which is definedonly by the appended claims.

As clear from the above explanation, according to one embodiment of thepresent invention, it is possible to realize an oscillating apparatusthat is able to stabilize a phase difference of an oscillation signalwith respect to a reference signal in a PLL circuit, and to provide thephase difference and the loop band that are changeable.

1. An oscillating apparatus comprising: an integration circuit thatoutputs a control signal based on an integration value of two inputtedvoltage values; an oscillator that outputs an oscillation signal of afrequency that is based on the control signal; a phase comparator thatoutputs a phase difference signal of a pulse width that is in accordancewith a phase difference between the oscillation signal and the referencesignal, by comparing the oscillation signal with a reference signal of apredetermined frequency; a controlling circuit that controls the twoinputted voltage values based on the phase difference signal, so as toapproximate a phase difference between the oscillation signal and thereference signal to a predetermined reference phase difference; and avoltage stabilizing circuit that defines the two inputted voltage valuesboth based on a predetermined reference voltage.
 2. The oscillatingapparatus as set forth in claim 1, wherein the controlling circuitgenerates a first voltage (V_(U)) and a second voltage (V_(D)), based onvoltage values respectively of a first terminal (U) and a secondterminal (D) of the phase comparator and further generates apredetermined phase controlling voltage (V_(C)).
 3. The oscillatingapparatus as set forth in claim 2, wherein the controlling circuit setsthe phase controlling voltage (V_(C)) and the first voltage (V_(D)) asone inputted voltage value with respect to the integration circuit, andthe second voltage (V_(U)) as the other inputted voltage value.